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pin configurations 8-lead narrow body so (r suffix) 18 7 6 5 3 4 8 7 6 5 top view (not to scale) adr293 v out v in gnd nc nc nc nc nc nc = no connect 2 8-lead tssop (ru suffix) 18 7 6 5 3 4 8 7 6 5 top view (not to scale) adr293 v out v in gnd nc nc nc nc nc nc = no connect 2 rev. a a low noise micropower 5.0 v, precision voltage reference adr293 features 6.0 v to 15 v supply range supply current 15 a max low noise 15 v pCp typ (0.1 hz to 10 hz) high output current 5 ma temperature range 40 c to 125 c pin compatible with ref02/ref19x applications portable instrumentation precision reference for 5 v systems a/d and d/a converter reference solar powered applications loop-current powered instruments general description the adr293 is a low noise, micropower precision voltage reference that utilizes an xfet ? (extra implanted junction fet) reference circuit. the new xfet architecture offers sig- nificant performance improvements over traditional bandgap and buried zener-based references. improvements include: one quarter the voltage noise output of bandgap references operating at the same current, very low and ultralinear temperature drift, low thermal hysteresis and excellent long-term stability. the adr293 is a series voltage reference providing stable and accurate output voltage from a 6.0 v supply. quiescent current is only 15 a max, making this device ideal for battery powered instrumentation. three electrical grades are available offering initial output accuracy of 3 mv, 6 mv, and 10 mv. tem- perature coefficients for the three grades are 8 ppm/ c, 15 ppm/ c and 25 ppm/ c max. line regulation and load regulation are typically 30 ppm/v and 30 ppm/ma, maintaining the reference? overall high performance. the adr293 is specified over the extended industrial tempera- ture range of ?0 c to +125 c. this device is available in the 8-lead soic and 8-lead tssop packages. xfet is a registered trademark of analog devices, inc. adr29x products output initial temperature voltage accuracy coefficient device (v) (%) (ppm/ c) max adr290 2.048 (see adr290/adr291/adr292 adr291 2.500 data sheet) adr292 4.096 adr293 5.000 0.06, 0.12, 0.20 8, 15, 25 one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781/329-4700 world wide web site: http://www.analog.com fax: 781/326-8703 ? analog devices, inc., 2001 information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of analog devices.
adr293?pecifications electrical specifications parameter symbol conditions min typ max unit initial accuracy output voltage v o i out = 0 ma ??grade 4.997 5.000 5.003 v ? +3 mv 0.06 % ??grade 4.994 5.000 5.006 v ? +6 mv 0.12 % ??grade 4.990 5.000 5.010 v ?0 +10 mv 0.20 % line regulation ?/f?grades ? v o / ? v in 6.0 v to 15 v, i out = 0 ma 30 100 ppm/v ??grade 40 150 ppm/v load regulation ?/f?grades ? v o / ? i load v s = 6.0 v, 0 ma to 5 ma 30 100 ppm/ma ??grade 40 150 ppm/ma long-term stability ? v o after 1000 hrs of operation @ 125 c 50 ppm noise voltage e n 0.1 hz to 10 hz 15 v p-p wideband noise density e n at 1 khz 640 nv/ hz electrical specifications parameter symbol conditions min typ max unit temperature coefficient ??grade tcv o i out = 0 ma 3 8 ppm/ c ??grade 5 15 ppm/ c ??grade 10 25 ppm/ c line regulation ?/f?grades ? v o / ? v in 6.0 v to 15 v, i out = 0 ma 35 150 ppm/v ??grade 50 200 ppm/v load regulation ?/f?grades ? v o / ? i load v s = 6.0 v, 0 ma to 5 ma 20 150 ppm/ma ??grade 30 200 ppm/ma electrical specifications parameter symbol conditions min typ max unit temperature coefficient ??grade tcv o i out = 0 ma 3 10 ppm/ c ??grade 5 20 ppm/ c ??grade 10 30 ppm/ c line regulation ?/f?grades ? v o / ? v in 6.0 v to 15 v, i out = 0 ma 40 200 ppm/v ??grade 70 250 ppm/v load regulation ?/f?grades ? v o / ? i load v s = 6.0 v, 0 ma to 5 ma 20 200 ppm/ma ??grade 30 300 ppm/ma supply current i s @ 25 c1115 a 15 20 a thermal hysteresis v o?ys so-8 72 ppm tssop-8 157 ppm specifications subject to change without notice. (v s = 6.0 v, t a = 25 c unless otherwise noted.) (v s = 6.0 v, t a = 40 c t a 125 c unless otherwise noted.) (v s = 6.0 v, t a = ?5 c t a 85 c unless otherwise noted.) rev. a C2C
adr293 rev. a C3C absolute maximum ratings 1 supply voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 v output short-circuit duration to gnd . . . . . . . . . . indefinite storage temperature range so, ru package . . . . . . . . . . . . . . . . . . . 65 c to 150 c operating temperature range . . . . . . . . . . 40 c to 125 c junction temperature range so, ru package . . . . . . . . . . . . . . . . . . . 65 c to 125 c lead temperature (soldering, 60 sec) . . . . . . . . . . . . . 300 c notes 1 stresses above those listed under absolute maximum ratings may cause perma- nent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those listed in the operational sections of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. 2 remove power before inserting or removing units from their sockets. caution esd (electrostatic discharge) sensitive device. electrostatic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge without detection. although the adr293 features proprietary esd protection circuitry, permanent damage may occur on devices subjected to high-energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality. warning! esd sensitive device package type ja * jc unit 8-lead soic (so) 158 43 c/w 8-lead tssop (ru) 240 43 c/w * ja is specified for worst-case conditions, i.e., ja is specified for device in socket testing; in practice, ja is specified for a device soldered in circuit board. ordering guide temperature output initial coefficient number of voltage accuracy max package package parts per model v % ppm/ c description option package adr293er, adr293er-reel7, adr293er-reel 5.00 0.06 8 soic so-8 98, 1000, 2500 adr293fr, adr293fr-reel7, adr293fr-reel 5.00 0.12 15 soic so-8 98, 1000, 2500 adr293gr, adr293gr-reel7, adr293gr-reel 5.00 0.20 25 soic so-8 98, 1000, 2500 ADR293GRU-reel7, ADR293GRU-reel 5.00 0.20 25 tssop ru-8 1000, 2500
adr293 rev. a C4C parameter definition line regulation , the change in output voltage due to a speci- fied change in input voltage. it includes the effects of self-heating. line regulation is expressed in either percent-per-volt, parts- per- million-per-volt, or microvolts-per-volt change in input voltage. load regulation, the change in output voltage due to a specified change in load current. it includes the effects of self-heating. load regulation is expressed in either microvolts-per-milliam- pere, parts-per-million-per-milliampere, or ohms of dc output resistance. long-term stability, typical shift of output voltage of 25 c on a sample of parts subjected to high-temperature operating life test of 1000 hours at 125 c. ? ? vvt?vt v ppm = vt?vt vt oo0 o1 o o0 o1 o0 = () () [] () () () 10 6 where: v o ( t 0 ) = v o at 25 c at time 0. v o ( t 1 ) = v o at 25 c after 1000 hours operation at 125 c. nc = no connect (there are in fact connections at nc pins which are reserved for manufacturing purposes. users should not connect anything at nc pins.). temperature coefficient , the change of output voltage over the operating temperature change and normalized by the output voltage at 25 c, expressed in ppm/ c. the equation follows: tcv ppm c vt vt vctt o oo o [/] () = () ? () () ? () 21 21 6 25 10 where: v o (25 c ) = v o at 25 c. v o ( t 1 ) = v o at temperature1. v o ( t 2 ) = v o at temperature2. thermal hysteresis , is defined as the change of output voltage after the device is cycled through temperature from +25 c to 40 c to +85 c and back to +25 c. this is a typical value from a sample of parts put through such a cycle. vvcv v ppm vcv vc o hys o o tc o hys ootc o __ _ _ () [] () () = = 25 25 25 10 6 where: v o (25 c ) = v o at 25 c. v o _tc =v o (25 c) after temperature cycle at +25 c to 40 c to +85 c and back to +25 c.
typical performance characteristics adr293 temperature ? c 5.006 4.994 output voltage ?v 5.004 5.002 5.000 4.998 4.996 3 typical parts v s 6.0v 125 100 75 50 25 0 ?5 ?0 tpc 1. v out vs. temperature input voltage v 16 0 supply current a 14 8 6 4 2 10 12 t a +125 c t a +25 c t a 40 c 16 14 12 10 8 6 4 2 0 tpc 2. supply current vs. input voltage temperature c 6 supply current a 16 14 12 10 8 v s 6.0v 125 100 75 50 25 0 25 50 tpc 3. supply current vs. temperature temperature c 0 line regulation ppm/v 100 80 60 40 20 v s 6.0v to 15v 125 100 75 50 25 0 25 50 tpc 4. line regulation vs. temperature temperature c 0 line regulation ppm/v 100 80 60 40 20 v s 6.0v to 9.0v i out 0ma 125 100 75 50 25 0 25 50 tpc 5. line regulation vs. temperature load current ma 0 0 5.0 differential voltage v 1.0 2.5 3.0 0.7 0.4 0.3 0.2 0.1 0.5 3.5 0.5 0.6 t a +125 c t a +25 c t a 40 c 1.5 2.0 4.0 4.5 &'(/ 0 1*
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adr293 rev. a C6C temperature c 0 load regulation ppm/ma 100 160 120 80 40 v s 6.0v i out 1ma i out 5ma 125 100 75 50 25 0 25 50 tpc 7. load regulation vs. temperature sourcing load current ma 010 v out from nominal mv 2 1 0 1 t a +125 c 1 2 3 4 t a 40 c t a +25 c tpc 8. ? v out from nominal vs. load current fre q uency hz 10 1000 voltage noise density nv/ hz 100 200 0 t a 25 c 400 600 800 1000 1200 v in 15v tpc 9. voltage noise density fre q uency hz 10 1000 ripple rejection db 100 20 0 40 60 80 100 120 v s 6.0v tpc 10. ripple rejection vs. frequency fre q uency hz 10 10k ripple rejection db 100 10 0 20 30 40 50 v s 6.0v i l 0ma 1k tpc 11. output impedance vs. frequency 1s 10 v p-p tpc 12. 0.1 hz to 10 hz noise
adr293 rev. a C7C 50 s i l 5ma 5v/div 2v/div tpc 13. turn-on time 50 s i l 5ma 5v/div 2v/div tpc 14. turn-off time 1ms i l 5ma tpc 15. load transient 1ms i l 5ma c l 1nf tpc 16. load transient 1ms i l 5ma c l 100nf tpc 17. load transient v out deviation ppm 18 16 0 200 40 160 frequency 120 80 40 0 240 80 120 160 200 14 12 10 8 6 4 2 temperature +25 c 40 c +85 c +25 c &'()3 &

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adr293 rev. a C8C device power dissipation considerations the adr293 is guaranteed to deliver load currents to 5 ma with an input voltage that ranges from 5.5 v to 15 v. when this device is used in applications with large input voltages, care should be exercised to avoid exceeding the published specifica- tions for maximum power dissipation or junction temperature that could result in premature device failure. the following formula should be used to calculate a device s maximum junc- tion temperature or dissipation: p tt d a a = ? j j in this equation, t j and t a are the junction and ambient tem- peratures, respectively, p d is the device power dissipation, and j a is the device package thermal resistance. basic voltage reference connections references, in general, require a bypass capacitor connected from the v out pin to the gnd pin. the circuit in figure 2 illustrates the basic configuration for the adr293. note that the decoupling capacitors are not required for circuit stability. adr293 1 2 3 4 8 7 6 5 nc nc nc nc output nc 0.1 f 0.1 f 10 f + nc = no connect figure 2. basic voltage reference configuration noise performance the noise generated by the adr293 is typically less than 15 v p-p over the 0.1 hz to 10 hz band. the noise measurement is made with a bandpass filter made of a 2-pole high-pass filter with a corner frequency at 0.1 hz and a 2-pole low-pass filter with a corner frequency at 10 hz. turn-on time upon application of power (cold start), the time required for the output voltage to reach its final value within a specified error band is defined as the turn-on settling time. two components normally associated with this are; the time for the active circuits to settle, and the time for the thermal gradients on the chip to stabilize. tpc 13 shows the typical turn-on time for the adr293. theory of operation the adr293 uses a new reference generation technique known as xfet, which yields a reference with low noise, low supply current and very low thermal hysteresis. the core of the xfet reference consists of two junction field- effect transistors one of which has an extra channel implant to raise its pinch-off voltage. by running the two jfets at the same drain current, the difference in pinch-off voltage can be amplified and used to form a highly stable voltage reference. the intrinsic reference voltage is around 0.5 v with a negative temperature coefficient of about 120 ppm/k. this slope is essentially locked to the dielectric constant of silicon and can be closely compensated by adding a correction term generated in the same fashion as the proportional-to-temperature (ptat) term used to compensate bandgap references. the big advan- tage over a bandgap reference is that the intrinsic temperature coefficient is some thirty times lower (therefore less correction is needed) and this results in much lower noise since most of the noise of a bandgap reference comes from the temperature com- pensation circuitry. the simplified schematic below shows the basic topology of the adr293. the temperature correction term is provided by a current source with value designed to be proportional to abso- lute temperature. the general equation is: vv rr r r ir out p ptat = ++ ? ? ? ? ? ? + ()() ? 12 3 1 3 where ? v p is the difference in pinch-off voltage between the two fets and i ptat is the positive temperature coefficient correction current. the process used for the xfet reference also features vertical npn and pnp transistors, the latter of which are used as output devices to provide a very low drop-out voltage. * * extra channel implant v out = r1+r2+r3 r1 v p + i ptat r3 i 1 i 1 i ptat v out v p r1 r2 r3 gnd v in figure 1. simplified schematic
adr293 rev. a C9C applications a negative precision reference without precision resistors in many current-output cmos dac applications where the output signal voltage must be of the same po larity as the reference vo ltage, it is often required to reconfigure a current- switching dac into a voltage-switching dac through the use of a 1.25 v reference, an op amp and a pair of resistors. using a current-switching dac directly requires the need for an additional operational amplifier at the output to reinvert the signal. a negative voltage reference is then desirable from the point that an additional operational amplifier is not required for either reinversion (current-switching mode) or amplifica- tion (voltage-switching mode) of the dac output voltage. in general, any positive voltage reference can be converted into a negative voltage reference through the use of an operational amplifier and a pair of matched resistors in an inverting configu- ration. the disadvantage to that approach is that the largest single source of error in the circuit is the relative matching of the resis- tors used. the circuit illustrated in figure 3 avoids the need for tightly matched resistors with the use of an active integrator circuit. in this circuit, the output of the voltage reference provides the input drive for the integrator. the integrator, to maintain circuit equilibrium, adjusts its output to establish the proper relation- ship between the reference s v out and gnd. one caveat with this approach should be mentioned: although rail-to-rail output amplifiers work best in the application, these operational ampli- fiers require a finite amount (mv) of headroom when required to provide any load current. the choice for the circuit s negative supply should take this issue into account. adr293 +5v 5v a 1 v ref 1 f 1k v out gnd v in 1 f 100k 100k a 1 = 1/2 op291, 1/2 op295 figure 3. a negative precision voltage reference uses no precision resistors a precision current source many times in low power applications, the need arises for a preci- sion current source that can operate on low supply voltages. as shown in figure 4, the adr293 is configured as a precision current source. the circuit configuration illustrated is a floating current source with a grounded load. the reference s output voltage is bootstrapped across r set , which sets the output current into the load. with this configuration, circuit precision is main- tained for load currents in the range from the reference s supply current, typically 15 a to approximately 5 ma. adr293 i sy adjust v out gnd v in 1 f r1 p1 r set i out r l figure 4. a precision current source
adr293 rev. a C10C kelvin connections in many portable instrumentation applications where pc board cost and area go hand-in-hand, circuit interconnects are very often of dimensionally minimum width. these narrow lines can cause large voltage drops if the voltage reference is required to provide load currents to various functions. in fact, a circuit s interconnects can exhibit a typical line resistance of 0.45 m ? /square (1 oz. cu, for example). force and sense connections also referred to as kelvin connections, offer a convenient method of eliminating the effects of voltage drops in circuit wires. load currents flowing through wiring resistance produce an error (v error = r i l ) at the load. however, the kelvin connection of figure 5 overcomes the problem by including the wiring resistance within the forcing loop of the op amp. since the op amp senses the load voltage, op amp loop control forces the output to compensate for the wiring error and to produce the correct voltage at the load. adr293 v out gnd v in v in r lw +v out sense +v out force r l r lw 100k 1 f a 1 figure 5. advantage of kelvin connection voltage regulator for portable equipment the adr293 is ideal for providing a stable, low cost and low power reference voltage in portable equipment power supplies. figure 6 shows how the adr293 can be used in a voltage regulator that not only has low output noise (as compared to switch mode design) and low power, but also a very fast recovery after current surges. some precautions should be taken in the selection of the output capacitors. too high an esr (effective series resistance) could endanger the stability of the circuit. a solid tantalum capacitor, 16 v or higher, and an aluminum elec- trolytic capacitor, 10 v or higher, are recommended for c1 and c2, respectively. also, the path from the ground side of c1 and c2 to the ground side of r1 should be kept as short as possible. adr293 v out gnd v in 0.1 f lead-acid battery + 6v charger input r1 402k 1% r2 402k 1% + c2 1000 f elect c1 68 f tant + 5v, 100ma irf9530 r3 510k op-20 figure 6. voltage regulator for portable equipment outline dimensions dimensions shown in inches and (mm). 8-lead narrow body so (so-8) 0.0098 (0.25) 0.0075 (0.19) 0.0500 (1.27) 0.0160 (0.41) 8 0 0.0196 (0.50) 0.0099 (0.25) 45 85 4 1 0.1968 (5.00) 0.1890 (4.80) 0.2440 (6.20) 0.2284 (5.80) pin 1 0.1574 (4.00) 0.1497 (3.80) 0.0500 (1.27) bsc 0.0688 (1.75) 0.0532 (1.35) seating plane 0.0098 (0.25) 0.0040 (0.10) 0.0192 (0.49) 0.0138 (0.35) 8-lead tssop (ru-8) 8 5 4 1 0.256 (6.50) 0.246 (6.25) 0.177 (4.50) 0.169 (4.30) pin 1 0.0256 (0.65) bsc 0.122 (3.10) 0.114 (2.90) seating plane 0.006 (0.15) 0.002 (0.05) 0.0118 (0.30) 0.0075 (0.19) 0.0433 (1.10) max 0.0079 (0.20) 0.0035 (0.090) 0.028 (0.70) 0.020 (0.50) 8 0 c00164C0C3/01 (a) printed in u.s.a.

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